TS4871 OUTPUT RAIL TO RAIL 1W AUDIO POWER AMPLIFIER WITH STANDBY MODE OPERATING FROM VCC = 2.5V to 5.5V PIN CONNECTIONS (Top View) 1W RAIL TO RAIL OUTPUT POWER @ Vcc=5V, THD=1%, f=1kHz, with 8 Load TS4871IST - MiniSO8 ULTRA LOW CONSUMPTION IN STANDBY MODE (10nA) Standby 1 8 VOUT2 Bypass 2 7 GND VIN+ 3 6 VCC VIN- 4 5 VOUT1 75dB PSRR @ 217Hz from 5V to 2.6V ULTRA LOW POP & CLICK ULTRA LOW DISTORTION (0.1%) UNITY GAIN STABLE AVAILABLE IN SO8, MiniSO8 & DFN8 3x3mm TS4871ID-TS4871IDT - SO8 DESCRIPTION Standby 1 8 VOUT2 Bypass 2 7 GND VIN+ 3 6 VCC VIN- 4 5 VOUT1 The TS4871 is an Audio Power Amplifier capable of delivering 1W of continuous RMS Ouput Power into 8 load @ 5V. This Audio Amplifier is exhibiting 0.1% distortion level (THD) from a 5V supply for a Pout = 250mW RMS. An external standby mode control reduces the supply current to less than 10nA. An internal thermal shutdown protection is also provided. TS4871IQT - DFN8 The TS4871 has been designed for high quality audio applications such as mobile phones and to minimize the number of external components. STANDBY 1 8 VOUT 2 BYPASS 2 7 GND VIN+ 3 6 Vcc VIN- 4 5 VOUT 1 The unity-gain stable amplifier can be configured by external gain setting resistors. APPLICATIONS Mobile Phones (Cellular / Cordless) Laptop / Notebook Computers TYPICAL APPLICATION SCHEMATIC Cfeed PDAs Rfeed Audio Input ORDER CODE -40, +85C Cin 4 3 VinVin+ - Vout1 5 + Package Marking D S Q * * RL 8 Ohms Vcc * 4871I 4871 2 Bypass 1 Standby Av=-1 + Vout2 8 Rstb Bias GND TS4871 Temperature Range: I Rin Cs Vcc Portable Audio Devices Part Number Vcc 6 Cb TS4871 7 MiniSO & DFN only available in Tape & Reel with T suffix(IST & IQT) D = Small Outline Package (SO) - also available in Tape & Reel (DT) June 2003 1/28 TS4871 ABSOLUTE MAXIMUM RATINGS Symbol VCC Vi Parameter Supply voltage 1) 2) Unit 6 V GND to VCC V Toper Operating Free Air Temperature Range -40 to + 85 C Tstg Storage Temperature Tj Rthja Pd Input Voltage -65 to +150 C Maximum Junction Temperature 150 C Thermal Resistance Junction to Ambient 3) SO8 MiniSO8 QNF8 175 215 70 Internally Limited4) 2 200 Class A 260 Power Dissipation ESD Human Body Model ESD Machine Model Latch-up Latch-up Immunity Lead Temperature (soldering, 10sec) 1. 2. 3. 4. Value C/W kV V C All voltages values are measured with respect to the ground pin. The magnitude of input signal must never exceed VCC + 0.3V / G ND - 0.3V Device is protected in case of over temperature by a thermal shutdown active @ 150C. Exceeding the power derating curves during a long period, involves abnormal operating condition. OPERATING CONDITIONS Symbol VCC Parameter Supply Voltage VICM Common Mode Input Voltage Range VSTB Standby Voltage Input : Device ON Device OFF RL Rthja 2.5 to 5.5 V V GND VSTB 0.5V VCC - 0.5V VSTB VCC V 4 - 32 1) 1. This thermal resistance can be reduced with a suitable PCB layout (see Power Derating Curves Fig. 20) 2. When mounted on a 4 layers PCB 2/28 Unit GND to VCC - 1.2V Load Resistor Thermal Resistance Junction to Ambient SO8 MiniSO8 DFN8 2) Value 150 190 41 C/W TS4871 ELECTRICAL CHARACTERISTICS VCC = +5V, GND = 0V, Tamb = 25C (unless otherwise specified) Symbol Typ. Max. Unit Supply Current No input signal, no load 6 8 mA Standby Current 1) No input signal, Vstdby = Vcc, RL = 8 10 1000 nA Voo Output Offset Voltage No input signal, RL = 8 5 20 mV Po Output Power THD = 1% Max, f = 1kHz, RL = 8 1 W 0.15 % Power Supply Rejection Ratio2) f = 217Hz, RL = 8, RFeed = 22K, Vripple = 200mV rms 75 dB M Phase Margin at Unity Gain RL = 8, CL = 500pF 70 Degrees GM Gain Margin RL = 8, CL = 500pF 20 dB GBP Gain Bandwidth Product RL = 8 2 MHz ICC ISTANDBY THD + N PSRR Parameter Min. Total Harmonic Distortion + Noise Po = 250mW rms, Gv = 2, 20Hz < f < 20kHz, RL = 8 1. Standby mode is actived when Vstdby is tied to Vcc 2. Dynamic measurements - 20*log(rms(Vout)/rms(Vripple)). Vripple is the surimposed sinus signal to Vcc @ f = 217Hz VCC = +3.3V, GND = 0V, Tamb = 25C (unless otherwise specified)3) Symbol Typ. Max. Unit Supply Current No input signal, no load 5.5 8 mA Standby Current 1) No input signal, Vstdby = Vcc, RL = 8 10 1000 nA Voo Output Offset Voltage No input signal, RL = 8 5 20 mV Po Output Power THD = 1% Max, f = 1kHz, RL = 8 450 mW Total Harmonic Distortion + Noise Po = 250mW rms, Gv = 2, 20Hz < f < 20kHz, RL = 8 0.15 % Power Supply Rejection Ratio2) f = 217Hz, RL = 8, RFeed = 22K, Vripple = 200mV rms 75 dB M Phase Margin at Unity Gain RL = 8, CL = 500pF 70 Degrees GM Gain Margin RL = 8, CL = 500pF 20 dB GBP Gain Bandwidth Product RL = 8 2 MHz ICC ISTANDBY THD + N PSRR Parameter Min. 1. Standby mode is actived when Vstdby is tied to Vcc 2. Dynamic measurements - 20*log(rms(Vout)/rms(Vripple)). Vripple is the surimposed sinus signal to Vcc @ f = 217Hz 3. All electrical values are made by correlation between 2.6V and 5V measurements 3/28 TS4871 ELECTRICAL CHARACTERISTICS VCC = 2.6V, GND = 0V, Tamb = 25C (unless otherwise specified) Symbol Typ. Max. Unit Supply Current No input signal, no load 5.5 8 mA Standby Current 1) No input signal, Vstdby = Vcc, RL = 8 10 1000 nA Voo Output Offset Voltage No input signal, RL = 8 5 20 mV Po Output Power THD = 1% Max, f = 1kHz, RL = 8 260 mW Total Harmonic Distortion + Noise Po = 200mW rms, Gv = 2, 20Hz < f < 20kHz, RL = 8 0.15 % Power Supply Rejection Ratio2) f = 217Hz, RL = 8, RFeed = 22K, Vripple = 200mV rms 75 dB M Phase Margin at Unity Gain RL = 8, CL = 500pF 70 Degrees GM Gain Margin RL = 8, CL = 500pF 20 dB GBP Gain Bandwidth Product RL = 8 2 MHz ICC ISTANDBY THD + N PSRR Parameter Min. 1. Standby mode is actived when Vstdby is tied to Vcc 2. Dynamic measurements - 20*log(rms(Vout)/rms(Vripple)). Vripple is the surimposed sinus signal to Vcc @ f = 217Hz Components Functional Description Rin Inverting input resistor which sets the closed loop gain in conjunction with Rfeed. This resistor also forms a high pass filter with Cin (fc = 1 / (2 x Pi x Rin x Cin)) Cin Input coupling capacitor which blocks the DC voltage at the amplifier input terminal Rfeed Feed back resistor which sets the closed loop gain in conjunction with Rin Cs Supply Bypass capacitor which provides power supply filtering Cb Bypass pin capacitor which provides half supply filtering Cfeed Rstb Gv Low pass filter capacitor allowing to cut the high frequency (low pass filter cut-off frequency 1 / (2 x Pi x Rfeed x Cfeed)) Pull-up resistor which fixes the right supply level on the standby pin Closed loop gain in BTL configuration = 2 x (Rfeed / Rin) REMARKS 1. All measurements, except PSRR measurements, are made with a supply bypass capacitor Cs = 100F. 2. External resistors are not needed for having better stability when supply @ Vcc down to 3V. By the way, the quiescent current remains the same. 3. The standby response time is about 1s. 4/28 TS4871 Fig. 1 : Open Loop Frequency Response Fig. 2 : Open Loop Frequency Response 0 -60 40 -80 -100 -120 -140 -60 -80 Phase -100 20 -120 -140 0 -160 -160 -180 -20 -180 -20 -200 -40 0.3 1 10 100 1000 -200 -220 10000 -40 0.3 1 10 Frequency (kHz) Fig. 3 : Open Loop Frequency Response 60 Vcc = 3.3V RL = 8 Tamb = 25C -60 -100 -120 20 -140 -160 0 Phase (Deg) Gain (dB) Phase Gain 60 -40 -80 40 0 80 -20 Gain (dB) Gain Vcc = 3.3V ZL = 8 + 560pF Tamb = 25C Phase 10 100 1000 Frequency (kHz) 10000 -140 -160 -180 -200 -20 -220 -40 0.3 -240 Fig. 5 : Open Loop Frequency Response Gain 60 Vcc = 2.6V RL = 8 Tamb = 25C 60 -40 -60 -120 20 -140 -160 0 10000 Vcc = 2.6V ZL = 8 + 560pF Tamb = 25C Phase -200 1 10 100 1000 Frequency (kHz) 10000 -240 -40 -60 -120 -140 -160 0 -180 -200 -20 -220 -220 -40 0.3 -20 -100 20 -180 -20 -240 -80 40 Gain (dB) -100 100 1000 Frequency (kHz) 0 Gain Phase (Deg) Gain (dB) Phase 10 80 -20 -80 40 1 Fig. 6 : Open Loop Frequency Response 0 80 -60 -120 0 -200 1 -40 -100 20 -220 -40 0.3 -20 -80 40 -180 -20 -220 10000 Fig. 4 : Open Loop Frequency Response 0 80 100 1000 Frequency (kHz) Phase (Deg) 0 -40 Phase (Deg) 20 -20 Vcc = 5V ZL = 8 + 560pF Tamb = 25C Phase (Deg) Gain -40 Phase Gain (dB) 60 Gain (dB) 40 0 -20 Vcc = 5V RL = 8 Tamb = 25C Gain Phase (Deg) 60 -40 0.3 1 10 100 1000 Frequency (kHz) 10000 -240 5/28 TS4871 Phase 60 100 -100 80 -120 60 Gain (dB) Gain -140 40 -160 20 0 -20 -40 0.3 -180 1 10 100 -40 0.3 -80 80 -100 Phase Gain (dB) Gain -140 40 -160 20 -180 0 -40 0.3 6/28 -200 Vcc = 2.6V CL = 560pF Tamb = 25C 1 10 -220 100 1000 Frequency (kHz) 10000 -240 Phase (Deg) -120 60 -20 -180 -220 Fig. 9 : Open Loop Frequency Response -140 -160 -20 10000 -120 20 -200 100 1000 Frequency (kHz) -100 Phase 40 0 Vcc = 5V CL = 560pF Tamb = 25C -80 Gain Gain (dB) 80 -80 Phase (Deg) 100 Fig. 8 : Open Loop Frequency Response -200 Vcc = 3.3V CL = 560pF Tamb = 25C 1 10 -220 100 1000 Frequency (kHz) 10000 -240 Phase (Deg) Fig. 7 : Open Loop Frequency Response TS4871 Fig. 10 : Power Supply Rejection Ratio (PSRR) vs Power supply Fig. 11 : Power Supply Rejection Ratio (PSRR) vs Feedback Capacitor -30 -10 Vripple = 200mVrms Rfeed = 22 Input = floating RL = 8 Tamb = 25C -50 -20 -30 PSRR (dB) PSRR (dB) -40 Vcc = 5V, 3.3V & 2.6V Cb = 1F & 0.1F -60 -40 Vcc = 5, 3.3 & 2.6V Cb = 1F & 0.1F Rfeed = 22k Vripple = 200mVrms Input = floating RL = 8 Tamb = 25C Cfeed=0 Cfeed=150pF Cfeed=330pF -50 -60 -70 -70 -80 10 100 1000 10000 Frequency (Hz) -80 10 100000 Fig. 12 : Power Supply Rejection Ratio (PSRR) vs Bypass Capacitor -10 Cb=10F PSRR (dB) -30 -40 1000 10000 Frequency (Hz) Cin=1F Cin=330nF Vcc = 5, 3.3 & 2.6V Rfeed = 22k Rin = 22k, Cin = 1F Rg = 100, RL = 8 Tamb = 25C -20 PSRR (dB) -20 100 Cb=47F -50 100000 Fig. 13 : Power Supply Rejection Ratio (PSRR) vs Input Capacitor -10 Cb=1F Cfeed=680pF Cin=220nF -30 Vcc = 5, 3.3 & 2.6V Rfeed = 22k, Rin = 22k Cb = 1F Rg = 100, RL = 8 Tamb = 25C -40 Cin=100nF -60 -70 -50 Cb=100F -80 10 -60 10 100 1000 10000 100000 Cin=22nF 100 1000 10000 100000 Frequency (Hz) Frequency (Hz) Fig. 14 : Power Supply Rejection Ratio (PSRR) vs Feedback Resistor -10 -20 PSRR (dB) -30 -40 Vcc = 5, 3.3 & 2.6V Cb = 1F & 0.1F Vripple = 200mVrms Input = floating RL = 8 Tamb = 25C Rfeed=110k Rfeed=47k -50 -60 Rfeed=22k -70 Rfeed=10k -80 10 100 1000 10000 Frequency (Hz) 100000 7/28 TS4871 Fig. 16 : Pout @ THD + N = 10% vs Supply Voltage vs RL Fig. 15 : Pout @ THD + N = 1% vs Supply Voltage vs RL 2.0 8 Gv = 2 & 10 Cb = 1F F = 1kHz BW < 125kHz Tamb = 25C 1.2 1.0 Output power @ 10% THD + N (W) Output power @ 1% THD + N (W) 1.4 6 4 0.8 16 0.6 0.4 0.2 32 0.0 2.5 3.0 3.5 4.0 4.5 Gv = 2 & 10 Cb = 1F F = 1kHz BW < 125kHz Tamb = 25C 1.8 1.6 1.4 4 1.2 1.0 16 0.8 0.6 0.4 0.2 32 0.0 2.5 5.0 8 3.0 3.5 4.5 5.0 Fig. 18 : Power Dissipation vs Pout 1.4 0.6 Vcc=5V 1.2 F=1kHz THD+N<1% Vcc=3.3V F=1kHz 0.5 THD+N<1% RL=4 Power Dissipation (W) Power Dissipation (W) Fig. 17 : Power Dissipation vs Pout 1.0 0.8 0.6 RL=8 0.4 RL=4 0.4 0.3 0.2 RL=8 0.1 0.2 RL=16 0.0 0.0 0.2 0.4 0.6 0.8 RL=16 1.0 1.2 0.0 0.0 1.4 0.2 Output Power (W) 0.4 0.6 0.8 Output Power (W) Fig. 19 : Power Dissipation vs Pout Fig. 20 : Power Derating Curves 0.40 2.0 Vcc=2.6V F=1kHz THD+N<1% 1.8 1.6 RL=4 0.30 Power Dissipation (W) Power Dissipation (W) 4.0 Vcc (V) Vcc (V) 0.35 6 0.25 0.20 0.15 RL=8 0.10 QFN8 1.4 1.2 1.0 SO8 0.8 0.6 0.4 0.05 0.00 0.0 RL=16 0.0 0.1 0.2 Output Power (W) 8/28 MiniSO8 0.2 0.3 0.4 0 25 50 75 100 Ambiant Temperature (C) 125 150 TS4871 Fig. 21 : THD + N vs Output Power Fig. 22 : THD + N vs Output Power 10 10 RL = 4, Vcc = 5V Gv = 10 Cb = Cin = 1F BW < 125kHz, Tamb = 25C THD + N (%) THD + N (%) Rl = 4 Vcc = 5V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C 1 20kHz 20kHz 1 20Hz 1kHz 20Hz, 1kHz 0.1 1E-3 0.01 0.1 Output Power (W) 0.1 1E-3 1 Fig. 23 : THD + N vs Output Power 1 Fig. 24 : THD + N vs Output Power 10 10 RL = 4, Vcc = 3.3V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C THD + N (%) THD + N (%) 0.01 0.1 Output Power (W) 1 RL = 4, Vcc = 3.3V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 20kHz 1 20kHz 0.1 20Hz 1kHz 20Hz, 1kHz 0.1 1E-3 0.01 0.1 Output Power (W) 1 Fig. 25 : THD + N vs Output Power 0.01 0.1 Output Power (W) 1 Fig. 26 : THD + N vs Output Power 10 RL = 4, Vcc = 2.6V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C THD + N (%) THD + N (%) 10 1E-3 1 RL = 4, Vcc = 2.6V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 1 20kHz 20kHz 20Hz 0.1 1kHz 20Hz, 1kHz 0.1 1E-3 0.01 Output Power (W) 0.1 1E-3 0.01 Output Power (W) 0.1 9/28 TS4871 Fig. 27 : THD + N vs Output Power Fig. 28 : THD + N vs Output Power 10 RL = 8 Vcc = 5V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C 1 20Hz, 1kHz THD + N (%) THD + N (%) 10 20kHz 0.1 RL = 8 Vcc = 5V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 1 20Hz 20kHz 0.1 1kHz 1E-3 0.01 0.1 Output Power (W) 1 1E-3 Fig. 29 : THD + N vs Output Power 1 Fig. 30 : THD + N vs Output Power 10 10 RL = 8, Vcc = 3.3V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C THD + N (%) THD + N (%) 0.01 0.1 Output Power (W) 1 RL = 8, Vcc = 3.3V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 1 20kHz 20Hz 20kHz 20Hz, 1kHz 0.1 0.1 1kHz 1E-3 0.01 0.1 Output Power (W) 1 Fig. 31 : THD + N vs Output Power 1 10 RL = 8, Vcc = 2.6V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C 1 20Hz, 1kHz 1E-3 RL = 8, Vcc = 2.6V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 1 20Hz 20kHz 20kHz 0.1 10/28 0.01 0.1 Output Power (W) Fig. 32 : THD + N vs Output Power THD + N (%) THD + N (%) 10 1E-3 0.1 0.01 Output Power (W) 0.1 1E-3 1kHz 0.01 Output Power (W) 0.1 TS4871 Fig. 33 : THD + N vs Output Power Fig. 34 : THD + N vs Output Power 10 RL = 8 Vcc = 5V Gv = 2 Cb = 0.1F, Cin = 1F BW < 125kHz Tamb = 25C 1 RL = 8, Vcc = 5V, Gv = 10 Cb = 0.1F, Cin = 1F BW < 125kHz, Tamb = 25C 20Hz THD + N (%) THD + N (%) 10 20Hz 20kHz 1kHz 1 20kHz 1kHz 0.1 0.1 1E-3 0.01 0.1 Output Power (W) 1 1E-3 Fig. 35 : THD + N vs Output Power 10 RL = 8, Vcc = 3.3V Gv = 2 Cb = 0.1F, Cin = 1F BW < 125kHz Tamb = 25C THD + N (%) RL = 8, Vcc = 3.3V, Gv = 10 Cb = 0.1F, Cin = 1F BW < 125kHz, Tamb = 25C 1 20Hz 20kHz 1 20kHz 20Hz 1kHz 1kHz 0.1 0.1 1E-3 0.01 0.1 Output Power (W) 1 Fig. 37 : THD + N vs Output Power 10 1E-3 0.01 0.1 Output Power (W) 1 Fig. 38 : THD + N vs Output Power 10 RL = 8, Vcc = 2.6V Gv = 2 Cb = 0.1F, Cin = 1F BW < 125kHz Tamb = 25C RL = 8, Vcc = 2.6V, Gv = 10 Cb = 0.1F, Cin = 1F BW < 125kHz, Tamb = 25C THD + N (%) THD + N (%) 1 Fig. 36 : THD + N vs Output Power 10 THD + N (%) 0.01 0.1 Output Power (W) 1 20Hz 20kHz 1 20kHz 1kHz 1kHz 0.1 1E-3 20Hz 0.1 0.01 Output Power (W) 0.1 1E-3 0.01 Output Power (W) 0.1 11/28 TS4871 Fig. 39 : THD + N vs Output Power Fig. 40 : THD + N vs Output Power 10 10 20kHz RL = 16, Vcc = 5V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 1 THD + N (%) THD + N (%) 1 RL = 16, Vcc = 5V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C 20kHz 0.1 0.1 1kHz 20Hz, 1kHz 0.01 1E-3 0.01 0.1 Output Power (W) 1 Fig. 41 : THD + N vs Output Power 0.01 1E-3 20kHz 0.1 1 RL = 16 Vcc = 3.3V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 20kHz 0.1 1kHz 20Hz 20Hz, 1kHz 0.01 1E-3 0.01 Output Power (W) 0.01 1E-3 0.1 Fig. 43 : THD + N vs Output Power THD + N (%) THD + N (%) 0.1 10 RL = 16 Vcc = 2.6V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C 20kHz 0.1 1 RL = 16 Vcc = 2.6V Gv = 10 Cb = Cin = 1F BW < 125kHz Tamb = 25C 20Hz 20kHz 0.1 20Hz, 1kHz 0.01 1E-3 12/28 0.01 Output Power (W) Fig. 44 : THD + N vs Output Power 10 1 1 10 RL = 16, Vcc = 3.3V Gv = 2 Cb = Cin = 1F BW < 125kHz Tamb = 25C THD + N (%) THD + N (%) 0.01 0.1 Output Power (W) Fig. 42 : THD + N vs Output Power 10 1 20Hz 0.01 Output Power (W) 1kHz 0.1 0.01 1E-3 0.01 Output Power (W) 0.1 TS4871 Fig. 45 : THD + N vs Frequency Pout = 1.2W RL = 4, Vcc = 5V Gv = 2 Cb = 1F BW < 125kHz Tamb = 25C 1 THD + N (%) THD + N (%) 1 Fig. 46 : THD + N vs Frequency Pout = 1.2W RL = 4, Vcc = 5V Gv = 10 Cb = 1F BW < 125kHz Tamb = 25C Pout = 600mW 0.1 20 100 1000 Frequency (Hz) 0.01 20 10000 Pout = 600mW 0.1 100 1000 Frequency (Hz) Fig. 47 : THD + N vs Frequency Fig. 48 : THD + N vs Frequency RL = 4, Vcc = 3.3V Gv = 2 Cb = 1F BW < 125kHz Tamb = 25C RL = 4, Vcc = 3.3V Gv = 10 Cb = 1F BW < 125kHz Tamb = 25C 1 THD + N (%) THD + N (%) 1 Pout = 540mW Pout = 540mW Pout = 270mW 100 1000 Frequency (Hz) Pout = 270mW Fig. 49 : THD + N vs Frequency THD + N (%) 1 0.1 20 10000 100 1000 Frequency (Hz) 10000 Fig. 50 : THD + N vs Frequency RL = 4, Vcc = 2.6V Gv = 2 Cb = 1F BW < 125kHz Tamb = 25C RL = 4, Vcc = 2.6V Gv = 10 Cb = 1F BW < 125kHz Tamb = 25C 1 Pout = 240mW THD + N (%) 0.1 20 10000 Pout = 240 & 120mW Pout = 120mW 0.1 20 100 1000 Frequency (Hz) 10000 0.1 20 100 1000 Frequency (Hz) 10000 13/28 TS4871 Fig. 51 : THD + N vs Frequency Fig. 52 : THD + N vs Frequency 1 Cb = 0.1F Cb = 1F RL = 8 Vcc = 5V Gv = 2 Pout = 450mW BW < 125kHz Tamb = 25C THD + N (%) THD + N (%) 1 RL = 8 Vcc = 5V Gv = 2 Pout = 900mW BW < 125kHz Tamb = 25C Cb = 0.1F Cb = 1F 0.1 100 1000 Frequency (Hz) Fig. 53 : THD + N vs Frequency THD + N (%) Cb = 0.1F RL = 8, Vcc = 5V Gv = 10 Pout = 450mW BW < 125kHz Tamb = 25C Cb = 0.1F 0.1 100 1000 Frequency (Hz) 10000 Fig. 55 : THD + N vs Frequency 20 100 1000 Frequency (Hz) 10000 Fig. 56 : THD + N vs Frequency 1 1 Cb = 0.1F Cb = 1F RL = 8, Vcc = 3.3V Gv = 2 Pout = 200mW BW < 125kHz Tamb = 25C THD + N (%) THD + N (%) RL = 8, Vcc = 3.3V Gv = 2 Pout = 400mW BW < 125kHz Tamb = 25C 0.1 14/28 10000 Cb = 1F 0.1 20 1000 Frequency (Hz) 1 Cb = 1F 20 100 Fig. 54 : THD + N vs Frequency RL = 8, Vcc = 5V Gv = 10 Pout = 900mW BW < 125kHz Tamb = 25C 1 0.1 20 10000 THD + N (%) 20 Cb = 0.1F Cb = 1F 0.1 100 1000 Frequency (Hz) 10000 20 100 1000 Frequency (Hz) 10000 TS4871 RL = 8, Vcc = 3.3V Gv = 10 Pout = 400mW BW < 125kHz Tamb = 25C 1 THD + N (%) Fig. 58 : THD + N vs Frequency Cb = 0.1F Cb = 1F RL = 8, Vcc = 3.3V Gv = 10 Pout = 200mW BW < 125kHz Tamb = 25C 1 THD + N (%) Fig. 57 : THD + N vs Frequency Cb = 0.1F Cb = 1F 0.1 0.1 20 100 1000 Frequency (Hz) 10000 Fig. 59 : THD + N vs Frequency 20 100 1000 Frequency (Hz) 10000 Fig. 60 : THD + N vs Frequency 1 THD + N (%) Cb = 0.1F RL = 8, Vcc = 2.6V Gv = 2 Pout = 220mW BW < 125kHz Tamb = 25C Cb = 1F RL = 8, Vcc = 2.6V Gv = 2 Pout = 110mW BW < 125kHz Tamb = 25C THD + N (%) 1 Cb = 0.1F Cb = 1F 0.1 100 1000 Frequency (Hz) 10000 Fig. 61 : THD + N vs Frequency THD + N (%) 100 1000 Frequency (Hz) 10000 Fig. 62 : THD + N vs Frequency RL = 8, Vcc = 2.6V Gv = 10 Pout = 220mW BW < 125kHz Tamb = 25C 1 20 Cb = 0.1F 1 Cb = 0.1F THD + N (%) 20 0.1 RL = 8, Vcc = 2.6V Gv = 10 Pout = 110mW BW < 125kHz Tamb = 25C Cb = 1F Cb = 1F 0.1 0.1 20 100 1000 Frequency (Hz) 10000 20 100 1000 Frequency (Hz) 10000 15/28 TS4871 Fig. 63 : THD + N vs Frequency Fig. 64 : THD + N vs Frequency 1 1 RL = 16, Vcc = 5V Gv = 10, Cb = 1F BW < 125kHz Tamb = 25C THD + N (%) THD + N (%) RL = 16, Vcc = 5V Gv = 2, Cb = 1F BW < 125kHz Tamb = 25C Pout = 310mW 0.1 Pout = 620mW 0.1 Pout = 310mW Pout = 620mW 0.01 20 100 1000 Frequency (Hz) 0.01 20 10000 Fig. 65 : THD + N vs Frequency 100 1000 Frequency (Hz) 10000 Fig. 66 : THD + N vs Frequency 1 1 THD + N (%) THD + N (%) RL = 16, Vcc = 3.3V Gv = 2, Cb = 1F BW < 125kHz Tamb = 25C Pout = 270mW 0.1 RL = 16, Vcc = 3.3V Gv = 10 Cb = 1F BW < 125kHz Tamb = 25C Pout = 270mW 0.1 Pout = 135mW Pout = 135mW 0.01 20 100 1000 Frequency (Hz) 20 10000 Fig. 67 : THD + N vs Frequency THD + N (%) RL = 16, Vcc = 2.6V Gv = 10, Cb = 1F BW < 125kHz Tamb = 25C Pout = 80mW 0.1 100 1000 Frequency (Hz) Pout = 160mW 0.1 Pout = 80mW Pout = 160mW 16/28 10000 1 RL = 16, Vcc = 2.6V Gv = 2, Cb = 1F BW < 125kHz Tamb = 25C 0.01 20 1000 Frequency (Hz) Fig. 68 : THD + N vs Frequency 1 THD + N (%) 100 10000 0.01 20 100 1000 Frequency (Hz) 10000 TS4871 Fig. 69 : Signal to Noise Ratio vs Power Supply with Unweighted Filter (20Hz to 20kHz) Fig. 70 : Signal to Noise Ratio vs Power Supply with Weighted Filter Type A 100 100 90 90 RL=4 RL=8 80 SNR (dB) SNR (dB) RL=16 70 Gv = 2 Cb = Cin = 1F THD+N < 0.4% Tamb = 25C 60 50 2.5 3.0 3.5 4.0 4.5 RL=8 RL=4 RL=16 80 Gv = 10 Cb = Cin = 1F THD+N < 0.7% Tamb = 25C 70 60 2.5 5.0 3.0 3.5 Fig. 71 : Signal to Noise Ratio vs Power Supply with Weighted Filter type A 5.0 7 Vstandby = 0V Tamb = 25C 6 100 RL=16 5 RL=4 RL=8 90 Icc (mA) SNR (dB) 4.5 Fig. 72 : Current Consumption vs Power Supply Voltage 110 80 4 3 2 Gv = 2 Cb = Cin = 1F THD+N < 0.4% Tamb = 25C 70 60 2.5 4.0 Vcc (V) Vcc (V) 3.0 3.5 4.0 4.5 1 0 5.0 0 1 2 3 4 5 Vcc (V) Vcc (V) Fig. 73 : Signal to Noise Ratio Vs Power Supply with Unweighted Filter (20Hz to 20kHz) Fig. 74 : Current Consumption vs Standby Voltage @ Vcc = 5V 90 7 Vcc = 5V Tamb = 25C 6 80 RL=8 70 RL=16 Icc (mA) SNR (dB) 5 RL=4 4 3 2 Gv = 10 Cb = Cin = 1F THD+N < 0.7% Tamb = 25C 60 50 2.5 3.0 3.5 4.0 Vcc (V) 4.5 5.0 1 0 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 Vstandby (V) 17/28 TS4871 Fig. 75 : Current Consumption vs Standby Voltage @ Vcc = 2.6V Fig. 76 : Current Consumption vs Standby Voltage @ Vcc = 3.3V 6 6 Vcc = 2.6V Tamb = 25C 5 4 Icc (mA) Icc (mA) 4 3 3 2 2 1 1 0 0.0 0.5 1.0 1.5 Vstandby (V) 2.0 0 0.0 2.5 0.5 1.0 2.5 3.0 1.0 Tamb = 25C 0.8 0.7 0.6 0.5 RL = 4 RL = 8 0.4 0.3 0.2 0.1 RL = 16 0.0 2.5 Tamb = 25C 0.9 Vout1 & Vout2 Clipping Voltage Low side (V) 0.9 3.0 3.5 4.0 4.5 0.8 0.7 0.6 RL = 4 0.5 RL = 8 0.4 0.3 0.2 0.1 RL = 16 0.0 2.5 5.0 3.0 Power supply Voltage (V) 3.5 4.0 4.5 5.0 Power supply Voltage (V) Fig. 79 : Vout1+Vout2 Unweighted Noise Floor Fig. 80 : Vout1+Vout2 A-weighted Noise Floor 120 Vcc = 2.5V to 5V, Tamb = 25 C Cb = Cin = 1 F Input Grounded BW = 20Hz to 20kHz (Unweighted) 100 Av = 10 80 60 40 Standby mode Av = 2 Output Noise Voltage ( V) 120 Output Noise Voltage ( V) 2.0 Fig. 78 : Clipping Voltage vs Power Supply Voltage and Load Resistor 1.0 Vcc = 2.5V to 5V, Tamb = 25 C Cb = Cin = 1 F Input Grounded BW = 20Hz to 20kHz (A-Weighted) 100 80 Av = 10 60 40 Standby mode Av = 2 20 20 0 0 20 18/28 1.5 Vstandby (V) Fig. 77 : Clipping Voltage vs Power Supply Voltage and Load Resistor Vout1 & Vout2 Clipping Voltage High side (V) Vcc = 3.3V Tamb = 25C 5 100 1000 Frequency (Hz) 10000 20 100 1000 Frequency (Hz) 10000 TS4871 APPLICATION INFORMATION Fig. 81 : Demoboard Schematic C1 R2 C2 R1 Vcc S1 Vcc Vcc S2 GND C6 + 100 R3 6 C3 C5 R4 C4 Pos input P2 S6 Vcc Neg. input P1 C7 100n 4 R5 VinVin+ 3 - Vout1 5 + C9 + 470 S5 Positive Input mode Vcc Av=-1 + Vcc R7 330k 2 Bypass 1 Standby S8 Standby Vout2 8 C10 + 470 Bias GND D1 PW ON GND S4 GND S7 R6 R8 OUT1 S3 TS4871 7 C11 + C12 1u C8 Fig. 82 : SO8 & MiniSO8 Demoboard Components Side 19/28 TS4871 Fig. 83 : SO8 & MiniSO8 Demoboard Top Solder Layer The output power is: Pout = (2 Vout RMS ) 2 (W ) RL For the same power supply voltage, the output power in BTL configuration is four times higher than the output power in single ended configuration. Gain In Typical Application Schematic (see page 1) In flat region (no effect of Cin), the output voltage of the first stage is: R fe ed Vout1 = - Vin -------------------- (V) Rin For the second stage : Vout2 = -Vout1 (V) Fig. 84 : SO8 & MiniSO8 Demoboard Bottom Solder Layer The differential output voltage is: Rfee d Vout2 - Vo ut1 = 2Vin -------------------- (V) Rin The differential gain named gain (Gv) for more convenient usage is: Vout2 - Vou t1 Rfee d Gv = --------------------------------------- = 2 -------------------Vin Rin Remark : Vout2 is in phase with Vin and Vout1 is 180 phased with Vin. It means that the positive terminal of the loudspeaker should be connected to Vout2 and the negative to Vout1. Low and high frequency response BTL Configuration Principle The TS4871 is a monolithic power amplifier with a BTL output type. BTL (Bridge Tied Load) means that each end of the load is connected to two single ended output amplifiers. Thus, we have : Single ended output 1 = Vout1 = Vout (V) Single ended output 2 = Vout2 = -Vout (V) And Vout1 - Vout2 = 2Vout (V) 20/28 In low frequency region, the effect of Cin starts. Cin with Rin forms a high pass filter with a -3dB cut off frequency. 1 F C L = -------------------------------- ( Hz ) 2 R in Cin In high frequency region, you can limit the bandwidth by adding a capacitor (Cfeed) in parallel on Rfeed. Its form a low pass filter with a -3dB cut off frequency. 1 F C H = ----------------------------------------------- ( Hz ) 2 Rfe ed Cfeed TS4871 Power dissipation and efficiency Hypothesis : * Voltage and current in the load are sinusoidal (Vout and Iout) * Supply voltage is a pure DC source (Vcc) Regarding the load we have: V O UT = V PEAK sin t (V) and V OU T I OU T = ----------------- (A) RL and VPEAK 2 P O U T = ---------------------- (W) 2 RL Then, the average current delivered by the supply voltage is: I CC AVG VPEAK = 2 -------------------- (A) R L The power delivered by the supply voltage is Psupply = Vcc IccAVG (W) Then, the power dissipated by the amplifier is Pdiss = Psupply - Pout (W) 2 2 Vcc P di ss = ---------------------- P OU T - P O UT (W) RL and the maximum value is obtained when: Pdiss ---------------------- = 0 P OU T 2 Vcc 2 2RL ----- = 78.5% 4 Decoupling of the circuit Two capacitors are needed to bypass properly the TS4871, a power supply bypass capacitor Cs and a bias voltage bypass capacitor Cb. Cs has especially an influence on the THD+N in high frequency (above 7kHz) and indirectly on the power supply disturbances. With 100F, you can expect similar THD+N performances like shown in the datasheet. If Cs is lower than 100F, in high frequency increases, THD+N and disturbances on the power supply rail are less filtered. To the contrary, if Cs is higher than 100F, those disturbances on the power supply rail are more filtered. Cb has an influence on THD+N in lower frequency, but its function is critical on the final result of PSRR with input grounded in lower frequency. If Cb is lower than 1F, THD+N increase in lower frequency (see THD+N vs frequency curves) and the PSRR worsens up If Cb is higher than 1F, the benefit on THD+N in lower frequency is small but the benefit on PSRR is substantial (see PSRR vs. Cb curve : fig.12). Note that Cin has a non-negligible effect on PSRR in lower frequency. Lower is its value, higher is the PSRR (see fig. 13). Pop and Click performance Pop and Click performance is intimately linked with the size of the input capacitor Cin and the bias voltage bypass capacitor Cb. and its value is: Pdiss max = The maximum theoretical value is reached when Vpeak = Vcc, so (W) Remark : This maximum value is only depending on power supply voltage and load values. The efficiency is the ratio between the output power and the power supply V P E A K P O UT = ------------------------ = ----------------------Psup ply 4V C C Size of Cin is due to the lower cut-off frequency and PSRR value requested. Size of Cb is due to THD+N and PSRR requested always in lower frequency. Moreover, Cb determines the speed that the amplifier turns ON. The slower the speed is, the softer the turn ON noise is. The charge time of Cb is directly proportional to 21/28 TS4871 the internal generator resistance 50k. Then, the charge time constant for Cb is b = 50kxCb (s) As Cb is directly connected to the non-inverting input (pin 2 & 3) and if we want to minimize, in amplitude and duration, the output spike on Vout1 (pin 5), Cin must be charged faster than Cb. The charge time constant of Cin is in = (Rin+Rfeed)xCin (s) Thus we have the relation in << b (s) 5Cs t D i s ch C s = -------------- = 83 ms Icc Now, we must consider the discharge time of Cb. At power OFF or standby ON, Cb is discharged by a 100k resistor. So the discharge time is about bDisch 3xCbx100k (s). In the majority of application, Cb=1F, then bDisch300ms >> tdischCs. Power amplifier design examples Given : The respect of this relation permits to minimize the pop and click noise. Remark : Minimize Cin and Cb has a benefit on pop and click phenomena but also on cost and size of the application. Example : your target for the -3dB cut off frequency is 100 Hz. With Rin=Rfeed=22 k, Cin=72nF (in fact 82nF or 100nF). With Cb=1F, if you choose the one of the latest two values of Cin, the pop and click phenomena at power supply ON or standby function ON/OFF will be very small 50 kx1F >> 44kx100nF (50ms >> 4.4ms). Increasing Cin value increases the pop and click phenomena to an unpleasant sound at power supply ON and standby function ON/OFF. Why Cs is not important in pop and click consideration ? Hypothesis : * Cs = 100F * Supply voltage = 5V * Supply voltage internal resistor = 0.1 * Supply current of the amplifier Icc = 6mA * * * * * * * Load impedance : 8 Output power @ 1% THD+N : 0.5W Input impedance : 10k min. Input voltage peak to peak : 1Vpp Bandwidth frequency : 20Hz to 20kHz (0, -3dB) Ambient temperature max = 50C SO8 package First of all, we must calculate the minimum power supply voltage to obtain 0.5W into 8. With curves in fig. 15, we can read 3.5V. Thus, the power supply voltage value min. will be 3.5V. Following equation the maximum Pdiss max = power 2 Vcc 2 2RL dissipation (W) with 3.5V we have Pdissmax=0.31W. Refer to power derating curves (fig. 20), with 0.31W the maximum ambient temperature will be 100C. This last value could be higher if you follow the example layout shown on the demoboard (better dissipation). The gain of the amplifier in flat region will be: At power ON of the supply, the supply capacitor is charged through the internal power supply resistor. So, to reach 5V you need about five to ten times the charging time constant of Cs (s = 0.1xCs (s)). Then, this time equal 50s to 100s << b in the majority of application. At power OFF of the supply, Cs is discharged by a constant current Icc. The discharge time from 5V to 0V of Cs is: 22/28 V OUTP P 2 2 R L P OUT G V = --------------------- = ------------------------------------ = 5.65 VINPP VINPP We have Rin > 10k. Let's take Rin = 10k, then Rfeed = 28.25k. We could use for Rfeed = 30k in normalized value and the gain will be Gv = 6. In lower frequency we want 20 Hz (-3dB cut off frequency). Then: So, we could use for Cin a 1F capacitor value TS4871 1 C IN = ------------------------------ = 795nF 2 RinF C L which gives 16Hz. In Higher frequency we want 20kHz (-3dB cut off frequency). The Gain Bandwidth Product of the TS4871 is 2MHz typical and doesn't change when the amplifier delivers power into the load. The first amplifier has a gain of: Rfee d ----------------- = 3 R in and the theoretical value of the -3dB cut-off higher frequency is 2MHz/3 = 660kHz. We can keep this value or limit the bandwidth by adding a capacitor Cfeed, in parallel on Rfeed. Then: C FE E D 1 = --------------------------------------- = 265pF 2 R F E E D F C H So, we could use for Cfeed a 220pF capacitor value that gives 24kHz. Now, we can calculate the value of Cb with the formula b = 50kxCb >> in = (Rin+Rfeed)xCin which permits to reduce the pop and click effects. Then Cb >> 0.8F. We can choose for Cb a normalized value of 2.2F that gives good results in THD+N and PSRR. In the following tables, you could find three another examples with values required for the demoboard. Remark : components with (*) marking are optional. Application n1 : 20Hz to 20kHz bandwidth and 6dB gain BTL power amplifier. Components : Designator Part Type R1 22k / 0.125W R4 22k / 0.125W R6 Short Cicuit R7 330k / 0.125W R8* (Vcc-Vf_led)/If_led C5 470nF C6 100F C7 100nF C9 Short Circuit C10 Short Circuit C12 1F S1, S2, S6, S7 2mm insulated Plug 10.16mm pitch S8 3 pts connector 2.54mm pitch P1 PCB Phono Jack D1* Led 3mm U1 TS4871ID or TS4871IS Application n2 : 20Hz to 20kHz bandwidth and 20dB gain BTL power amplifier. Components : Designator Part Type R1 110k / 0.125W R4 22k / 0.125W R6 Short Cicuit R7 330k / 0.125W R8* (Vcc-Vf_led)/If_led C5 470nF C6 100F C7 100nF 23/28 TS4871 Designator Part Type Application n4 : Differential inputs BTL power amplifier. C9 Short Circuit C10 Short Circuit C12 1F S1, S2, S6, S7 2mm insulated Plug 10.16mm pitch We have also : R4 = R5, R1 = R6, C4 = C5. S8 3 pts connector 2.54mm pitch The gain of the amplifier is: P1 PCB Phono Jack D1* Led 3mm U1 TS4871ID or TS4871IS Application n3 : 50Hz to 10kHz bandwidth and 10dB gain BTL power amplifier. In this configuration, we need to place these components : R1, R4, R5, R6, R7, C4, C5, C12. R1 G V D I FF = 2 -------R4 For Vcc=5V, a 20Hz to 20kHz bandwidth and 20dB gain BTL power amplifier you could follow the bill of material below. Components : Components : Designator Designator Part Type Part Type R1 33k / 0.125W R1 110k / 0.125W R2 Short Circuit R4 22k / 0.125W R4 22k / 0.125W R5 22k / 0.125W R6 Short Cicuit R6 110k / 0.125W R7 330k / 0.125W R7 330k / 0.125W R8* (Vcc-Vf_led)/If_led R8* (Vcc-Vf_led)/If_led C2 470pF C4 470nF C5 150nF C5 470nF C6 100F C6 100F C7 100nF C7 100nF C9 Short Circuit C9 Short Circuit C10 Short Circuit C10 Short Circuit C12 1F C12 1F 2mm insulated Plug 10.16mm pitch D1* Led 3mm S1, S2, S6, S7 S1, S2, S6, S7 S8 3 pts connector 2.54mm pitch 2mm insulated Plug 10.16mm pitch P1 PCB Phono Jack D1* U1 24/28 S8 3 pts connector 2.54mm pitch Led 3mm P1, P2 PCB Phono Jack TS4871ID or TS4871IS U1 TS4871ID or TS4871IS TS4871 Note on how to use the PSRR curves Fig. 86 : PSRR measurement schematic (page 7) We have finished a design and we have chosen the components values : Rfeed 6 * Rin=Rfeed=22k * Cin=100nF * Cb=1F Vcc Vripple Vcc 4 Rin 3 VinVin+ - Vout1 5 Vs- + Cin Rg 100 Ohms 2 Bypass 1 Standby Vout2 8 Vs+ Bias GND Now, on fig. 13, we can see the PSRR (input grounded) vs frequency curves. At 217Hz we have a PSRR value of -36dB. In reality we want a value about -70dB. So, we need a gain of 34dB ! Now, on fig. 12 we can see the effect of Cb on the PSRR (input grounded) vs. frequency. With Cb=100F, we can reach the -70dB value. RL Av=-1 + Cb TS4871 7 Principle of operation The process to obtain the final curve (Cb=100F, Cin=100nF, Rin=Rfeed=22k) is a simple transfer point by point on each frequency of the curve on fig. 13 to the curve on fig. 12. The measurement result is shown on the next figure. Fig. 85 : PSRR changes with Cb PSRR (dB) -40 Cin=100nF Cb=1F Cin=100nF Cb=100F High/low cut-off frequencies -70 10 100 R ms ( V r i p pl e ) --------------------------------------------Rms ( Vs + - Vs - ) Remark : The measure of the Rms voltage is not a Rms selective measure but a full range (2 Hz to 125 kHz) Rms measure. It means that we measure the effective Rms signal + the noise. -50 -60 The PSRR value for each frequency is: PSRR ( d B ) = 20 x Log 10 Vcc = 5, 3.3 & 2.6V Rfeed = 22k, Rin = 22k Rg = 100, RL = 8 Tamb = 25C -30 * We fixed the DC voltage supply (Vcc), the AC sinusoidal ripple voltage (Vripple) and no supply capacitor Cs is used 1000 10000 100000 For their calculation, please check this "Frequency Response Gain vs Cin, & Cfeed" graph: Frequency (Hz) 10 5 What is the PSRR ? Gain (dB) 0 The PSRR is the Power Supply Rejection Ratio. It's a kind of SVR in a determined frequency range. The PSRR of a device, is the ratio between a power supply disturbance and the result on the output. We can say that the PSRR is the ability of a device to minimize the impact of power supply disturbances to the output. Cfeed = 330pF Cfeed = 680pF -5 -10 -15 -20 -25 10 Cin = 470nF Cfeed = 2.2nF Cin = 22nF Cin = 82nF Rin = Rfeed = 22k Tamb = 25C 100 1000 Frequency (Hz) 10000 How do we measure the PSRR ? 25/28 TS4871 PACKAGE MECHANICAL DATA SO-8 MECHANICAL DATA DIM. mm. MIN. TYP inch MAX. MIN. TYP. MAX. A 1.35 1.75 0.053 0.069 A1 0.10 0.25 0.04 0.010 A2 1.10 1.65 0.043 0.065 B 0.33 0.51 0.013 0.020 C 0.19 0.25 0.007 0.010 D 4.80 5.00 0.189 0.197 E 3.80 4.00 0.150 0.157 e 1.27 0.050 H 5.80 6.20 0.228 0.244 h 0.25 0.50 0.010 0.020 L 0.40 1.27 0.016 0.050 k ddd 8 (max.) 0.1 0.04 0016023/C 26/28 TS4871 PACKAGE MECHANICAL DATA 27/28 TS4871 PACKAGE MECHANICAL DATA Information furnished is believed to be accurate and reliable. However, STMicroelectronics assumes no responsibility for the consequences of use of such information nor for any infringement of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of STMicroelectronics. Specifications mentioned in this publication are subject to change without notice. This publication supersedes and replaces all information previously supplied. STMicroelectronics products are not authorized for use as critical components in life support devices or systems without express written approval of STMicroelectronics. (c) The ST logo is a registered trademark of STMicroelectronics (c) 2003 STMicroelectronics - Printed in Italy - All Rights Reserved STMicroelectronics GROUP OF COMPANIES Australia - Brazil - Canada - China - Finland - France - Germany - Hong Kong - India - Israel - Italy - Japan - Malaysia Malta - Morocco - Singapore - Spain - Sweden - Switzerland - United Kingdom - United States (c) http://www.st.com 28/28