Electrical Characteristics (Continued)
(Note 7) T
A
=25˚C, V
+
=15 V
DC
, unless otherwise stated
Parameter Conditions LM2900 LM3900 LM3301 Units
Min Typ Max Min Typ Max Min Typ Max
Mirror Gain @20 µA (Note 4) 0.90 1.0 1.1 0.90 1.0 1.1 0.90 1 1.10 µA/µA
@200 µA (Note 4) 0.90 1.0 1.1 0.90 1.0 1.1 0.90 1 1.10
∆Mirror Gain @20 µA to 200 µA (Note 4) 2 5 2 5 2 5 %
Mirror Current (Note 5) 10 500 10 500 10 500 µA
DC
Negative Input Current T
A
=25˚C (Note 6) 1.0 1.0 1.0 mA
DC
Input Bias Current Inverting Input 300 300 nA
Note 1: “Absolute Maximum Ratings” indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
functional, but do not guarantee specific performance limits.
Note 2: For operating at high temperatures, the device must be derated based on a 125˚C maximum junction temperature and a thermal resistance of 92˚C/W which
applies for the device soldered in a printed circuit board, operating in a still air ambient. Thermal resistance for the S.O. package is 131˚C/W.
Note 3: The output current sink capability can be increased for large signal conditions by overdriving the inverting input. This is shown in the section on Typical Char-
acteristics.
Note 4: This spec indicates the current gain of the current mirror which is used as the non-inverting input.
Note 5: Input VBE match between the non-inverting and the inverting inputs occurs for a mirror current (non-inverting input current) of approximately 10 µA. This is
therefore a typical design center for many of the application circuits.
Note 6: Clamp transistors are included on the IC to prevent the input voltages from swinging below ground more than approximately −0.3 VDC. The negative input
currents which may result from large signal overdrive with capacitance input coupling need to be externally limited to values of approximately 1 mA. Negative input
currents in excess of 4 mA will cause the output voltage to drop to a low voltage. This maximum current applies to any one of the input terminals. If more than one
of the input terminals are simultaneously driven negative smaller maximum currents are allowed. Common-mode current biasing can be used to prevent negative in-
put voltages; see for example, the “Differentiator Circuit” in the applications section.
Note 7: These specs apply for −40˚C ≤TA≤+85˚C, unless otherwise stated.
Note 8: Human body model, 1.5 kΩin series with 100 pF.
Application Hints
When driving either input from a low-impedance source, a
limiting resistor should be placed in series with the input lead
to limit the peak input current. Currents as large as 20 mA
will not damage the device, but the current mirror on the
non-inverting input will saturate and cause a loss of mirror
gain at mAcurrent levels—especially at high operating tem-
peratures.
Precautions should be taken to insure that the power supply
for the integrated circuit never becomes reversed in polarity
or that the unit is not inadvertently installed backwards in a
test socket as an unlimited current surge through the result-
ing forward diode within the IC could cause fusing of the in-
ternal conductors and result in a destroyed unit.
Output short circuits either to ground or to the positive power
supply should be of short time duration. Units can be de-
stroyed, not as a result of the short circuit current causing
metal fusing, but rather due to the large increase in IC chip
dissipation which will cause eventual failure due to exces-
sive junction temperatures. For example, when operating
from a well-regulated +5 V
DC
power supply at T
A
=25˚C with
a 100 kΩshunt-feedback resistor (from the output to the in-
verting input) a short directly to the power supply will not
cause catastrophic failure but the current magnitude will be
approximately 50 mA and the junction temperature will be
above T
J
max. Larger feedback resistors will reduce the cur-
rent, 11 MΩprovides approximately 30 mA, an open circuit
provides 1.3 mA, and a direct connection from the output to
the non-inverting input will result in catastrophic failure when
the output is shorted to V
+
as this then places the
base-emitter junction of the input transistor directly across
the power supply. Short-circuits to ground will have magni-
tudes of approximately 30 mA and will not cause cata-
strophic failure at T
A
=25˚C.
Unintentional signal coupling from the output to the
non-inverting input can cause oscillations. This is likely only
in breadboard hook-ups with long component leads and can
be prevented by a more careful lead dress or by locating the
non-inverting input biasing resistor close to the IC. A quick
check of this condition is to bypass the non-inverting input to
ground with a capacitor. High impedance biasing resistors
used in the non-inverting input circuit make this input lead
highly susceptible to unintentional AC signal pickup.
Operation of this amplifier can be best understood by notic-
ing that input currents are differenced at the inverting-input
terminal and this difference current then flows through the
external feedback resistor to produce the output voltage.
Common-mode current biasing is generally useful to allow
operating with signal levels near ground or even negative as
this maintains the inputs biased at +V
BE
. Internal clamp tran-
sistors (Note 6) catch-negative input voltages at approxi-
mately −0.3 V
DC
but the magnitude of current flow has to be
limited by the external input network. For operation at high
temperature, this limit should be approximately 100 µA.
This new “Norton” current-differencing amplifier can be used
in most of the applications of a standard IC op amp. Perfor-
mance as a DC amplifier using only a single supply is not as
precise as a standard IC op amp operating with split supplies
but is adequate in many less critical applications. New func-
tions are made possible with this amplifier which are useful
in single power supply systems. For example, biasing can be
designed separately from the AC gain as was shown in the
“inverting amplifier,” the “difference integrator” allows con-
trolling the charging and the discharging of the integrating
capacitor with positive voltages, and the “frequency doubling
tachometer” provides a simple circuit which reduces the
ripple voltage on a tachometer output DC voltage.
3 www.national.com
PrintDate=1998/04/29 PrintTime=11:07:21 39954 ds007936 Rev. No. 3 cmserv Proof 3